Nixie Tubes are cool retro looking decimal digit displays useful for many modern DIY projects like the venerable Nixie tube digital clock.   The Nixie tube, invented in the 1950’s, can provide a great fusion of old display technology with new innovations.  Unfortunately, one major difficulty in using them is that Nixie tubes need voltages up to 170V to energize.  While this voltage can be made several ways, a convenient way and the subject of this blog is to generate this voltage from a 5v supply.  This will allow the use of the same 5v supply used to power the Raspberry Pi, Esp8266, Arduino or other microcontroller that controls the display or IOT project.  Most solutions already available on the internet required a 9-16v input supply.     This design will operate from a 5v supply input supply, minimize the PCB footprint and use low profile and readily available parts to maximize the space available to the Nixie tubes.    In this blog, the schematic, Layout,  design equations, and simulations of the design are provided.  Not counting the circuit board, the maximum component height of the proposed design is 10mm (the inductor) and the footprint size is just 14.5cm squared.   The calculated efficiency is over 90%.    Of course, no design is complete until you confirm with experimental results.   In Part 2, we will discuss the final results and experimental verification.

Nixie Tube Power Supply Schematic: Updated From Part 2


Small Footprint, 14.5 cm2 footprint.  Four Mounting Holes, USB-Micro B connector for the 5v input.

Low Profile,  L3 Inductor height is 10mm above PCB.

PCB Layout Design Considerations

The PCB Layout was designed to be a building block component with four mounting holes, a USB micro B input connector and a terminal block output connector.   Attention was made to maximize the ground plane, use a shielded power inductor, EMI beads (L2 and L5), and maximize bulk capacitance to minimize conducted and Radiated EMI noise.

  1. Input voltage: 5v.
  2.        Output Voltage: 170v
  3.        Maximum Design Current: 20mA
  4.        Input capacitance:  200uF
  5.        Output Capacitance: 2uF
  6.        Switching Frequency: 50kHz
  7.        10mm Max Component Height (by Inductor)
  8.        14.5cm^2 Footprint size.
  9.        Input Connector: USB Micro b
  10. Output Connector: Terminal Block
  11.        M2 Sized Mounting Holes
  12. Shielded Inductor
  13.        EMI Beads in series with 5v Input and 160v output Nets

Design Files

All the files for the KiCad Schematic, Kicad Layout, Spice Simulations, and efficiency Calculations are available on Github.

  1. Kicad Schematic, PCB Layout, BOM
  2. Spice Simulations (LTSpice (TM))
  3. Boost Converter Efficiency Calculations

DCM Boost Converter Topology Design

This design uses the discontinuous conduction mode (DCM) boost converter topology to achieve the high 170v output voltage, high efficiency, fast transient,  and small footprint.   DCM gets its name because the boost inductor current resets to zero amps every switching cycle.   Two other possible design approaches are the continuous conduction mode (CCM) boost converter and the flyback converter.  With only a 5v input, the CCM boost converter is extremely limited in transient performance and has an extremely hard time to reach a 170v output voltage (the duty ratio must be more than 97%), while the flyback requires a custom transformer and you need to deal with leakage inductance losses.   From an efficiency point of view, the DCM boost converter looks quite good and is comparable and possibly better than both of these approaches.  for a low profile power supply, it is hard to beat the DCM boost converter and the simulations and equations shown later back this up.

Design Overview

The design focused on achieving 170v output voltage with the highest efficiency possible and with the smallest footprint.  The 5v to 170v DCM boost converter design is managed by the TI UCC3803 controller.  This controller has the advantage of operating from a 5v supply.  The discontinuous conduction mode (DCM) of operation was chosen for this design to ensure we could reach the high output voltage and low profile without the need for a custom flyback transformer winding.    The 33uH power inductor ensures DCM at 50kHz switching frequency up to the maximum full power (3.6Watts). The peak current is limited to around 4amps by resistors R8, R10 and R12.   The DCM mode of operation also allows for a fast response and simple compensation method.  The input and output capacitors are all surface mount ceramic capacitors for ultra-low footprint, long lifetime, Good filtering and minimal ESR.  Additional ferrite beads L2 and L5 reduce input and output ripple further and help with EMI.  The soft start time was increased by C14 from the default 4ms value programmed into the UCC3808 to approximately 20ms.

Key Design Specifications

(boost flyback design.xlsx file at Github site shows the complete calculations)

  • Input Voltage (Vin): 5v
  • Output Voltage (Vout): 170v
  • Output Load Current (Io): 6 x 3ma = 18ma
  • Maximum input power (Pmax): 3.6Watts
  • Power Inductor: 33uH
  • Typical Duty ratio at full power: 63%
  • Inductor Ripple Current (Pmax): 1.9A
  • RMS Power FET current : 870mA

Calculating Duty Ratio

A DCM boost converter does not follow the same conversion ratio found with a CCM mode boost, namely that D = 1- Vin/Vout, where D is the power FET duty ratio.   Instead, in DCM, the duty ratio is governed by the following equation:

Duty Ratio of the DCM boost Converter.  Io is output current, Ts is switching Period. L is the chosen inductance.Enter a caption

Where Io is the output current, L is the Power Inductor, Ts is the switching period (1/F).  With the above equation and the proper inductor value, the duty ratio of the DCM boost required to reach 170v will be less than 97% (the value of Duty for the CCM boost) and will bring with it some nice advantages.   In this design, the nominal duty ratio at full power is close to 60%.

Design starts with the Inductor Equation

The first step of the design was to choose a power Inductor so that the DCM mode of operation was maintained all the way to the maximum power.   The following equation determines the maximum inductor value.    In general, the higher the inductance, the lower the system losses.  However, in practice, a value about 50% of this value is needed to provide fast loop regulation and account for component losses that counter the ability to generate the high output voltage of 170v.

Power Inductor Value Required for DCM Boost Operation

Where Po is the output power.    The calculations from the equation above give a value of approximately 80uH.    The final value chosen was 33uH, about 50% of the calculated value.

Ultra Fast Regulation

A spice simulation shows the fast transient response, stable compensation, and good regulation with this DCM topology.  The DCM mode of operation designed to operate around 60% duty ratio at full power provides the fast regulation.   At 60% duty ratio, there is plenty of control range (i.e. 60% to 100%) to maintain the output voltage. Also, since the inductor energy is fully transferred to the output each cycle,  the plant mode of the converter is reduced and the duty ratio can be rapidly changed without having to worry about the inductor dynamics since you start at zero current each cycle.   Capacitor C6 of 100pF is used to place a zero before the loop gain crossover frequency to add phase margin.       With a full load step response, the output voltage drops only 1v (less than 1% from 170v).

18mA Step Load Response.  Output Voltage (Green Waveform) dips less than 1v.    A well-damped Response

LTSpice (TM) Simulation File of the DCM Boost Converter

The step response above also shows a well-damped recovery response, representing a   phase margin of more than 45 degrees.

Calculated 91% Efficiency at full power

The DCM boost converter has zero Diode reverse recovery losses and does not have any flyback transformer leakage inductance loses,  offsetting the higher RMS losses in the power FET and sense resistor.    While the complete efficiency calculation worksheet is available at Github, the four losses from the power FET, power diode and power inductor equations are shown below.

  • Power Fet conduction Loss:   68mW
  • Sense Resistor Loss: 75mW
  • Diode Conduction Loss:  11mW
  • Power Inductor Conduction Loss: 35mW
  • Total Calculated losses including snubber loss and gate drive: 264mW

Power FET Conduction Loss:

The equation below shows the Power Fet Losses are directly related to the power FET Rdson value.   In this design, the chosen power FET, FDS2672CT, has a nominal value of 90mOhm to minimize this value.

Power Fet Conduction Loss.

Sense Resistor Conduction Loss:

The sense resistor is the low ohmic resistor in series with the power FET.  This resistor is used by the UCC3803 to control the peak current of the power switch.    The equation is just like the Power Fet Loss with the Rdson replaced by the sense resistance, Rsense.  In this design the Rsense value is 100mOhms.

Sense Resistor Conduction Loss

Power Diode Conduction Loss:

The power diode losses equal the diode on voltage multiplied by the average diode current.   For the power diode in this design, the DFLS1200-7 is a Schottky type and has an on-voltage of 0.4V.

Power Diode Conduction Loss

Power Inductor Conductive loss:

The conduction losses in the power inductor are also directly related to the equivalent series resistance.  In this design, the power inductor has a Resr = 45mOhm.

Power Inductor Loss

Next Steps

The next step is a verification of the design.   The board is being manufactured and I’ll follow this up with experimental efficiency, step response results.    I would like get your questions or comments so please comment below.